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In electrical engineering and control theory, a **Bode plot** /ˈboʊdi/ is a graph of the frequency response of a system. It is usually a combination of a **Bode magnitude plot,** expressing the magnitude (usually in decibels) of the frequency response, and a **Bode phase plot,** expressing the phase shift.

- Overview
- Definition
- Frequency response
- Rules for handmade Bode plot
- Straight-line amplitude plot
- Corrected amplitude plot
- Straight-line phase plot
- Example
- Magnitude plot
- Phase plot
- Normalized plot
- An example with zero and pole
- Gain margin and phase margin
- Examples using Bode plots
- Bode plotter
- Related plots
- Appendix
- Proof for the relation to frequency response
- See also
- Notes
- References
- External links

As originally conceived by Hendrik Wade Bode in the 1930s, the plot is an asymptotic approximation of the frequency response, using straight line segments.^{ [1] }

Among his several important contributions to circuit theory and control theory, engineer Hendrik Wade Bode, while working at Bell Labs in the 1930s, devised a simple but accurate method for graphing gain and phase-shift plots. These bear his name, *Bode gain plot* and *Bode phase plot*. "Bode" is often pronounced /ˈboʊdi/ *BOH-dee* although the Dutch pronunciation is Bo-duh. (Dutch: [ˈboːdə] ).^{ [2] }^{ [3] }

Bode was faced with the problem of designing stable amplifiers with feedback for use in telephone networks. He developed the graphical design technique of the Bode plots to show the gain margin and phase margin required to maintain stability under variations in circuit characteristics caused during manufacture or during operation.^{ [4] } The principles developed were applied to design problems of servomechanisms and other feedback control systems. The Bode plot is an example of analysis in the frequency domain.

The Bode plot for a linear, time-invariant system with transfer function ( being the complex frequency in the Laplace domain) consists of a magnitude plot and a phase plot.

The **Bode magnitude plot** is the graph of the function of frequency (with being the imaginary unit). The -axis of the magnitude plot is logarithmic and the magnitude is given in decibels, i.e., a value for the magnitude is plotted on the axis at .

The **Bode phase plot** is the graph of the phase, commonly expressed in degrees, of the transfer function as a function of . The phase is plotted on the same logarithmic -axis as the magnitude plot, but the value for the phase is plotted on a linear vertical axis.

This section illustrates that a Bode Plot is a visualization of the frequency response of a system.

Consider a linear, time-invariant system with transfer function . Assume that the system is subject to a sinusoidal input with frequency ,

that is applied persistently, i.e. from a time to a time . The response will be of the form

i.e., also a sinusoidal signal with amplitude shifted in phase with respect to the input by a phase .

It can be shown^{ [5] } that the magnitude of the response is

**(1)**

and that the phase shift is

**(2)**

A sketch for the proof of these equations is given in the appendix.

In summary, subjected to an input with frequency the system responds at the same frequency with an output that is amplified by a factor and phase-shifted by . These quantities, thus, characterize the frequency response and are shown in the Bode plot.

For many practical problems, the detailed Bode plots can be approximated with straight-line segments that are asymptotes of the precise response. The effect of each of the terms of a multiple element transfer function can be approximated by a set of straight lines on a Bode plot. This allows a graphical solution of the overall frequency response function. Before widespread availability of digital computers, graphical methods were extensively used to reduce the need for tedious calculation; a graphical solution could be used to identify feasible ranges of parameters for a new design.

The premise of a Bode plot is that one can consider the log of a function in the form:

as a sum of the logs of its zeros and poles:

This idea is used explicitly in the method for drawing phase diagrams. The method for drawing amplitude plots implicitly uses this idea, but since the log of the amplitude of each pole or zero always starts at zero and only has one asymptote change (the straight lines), the method can be simplified.

Amplitude decibels is usually done using to define decibels. Given a transfer function in the form

where and are constants, , , and is the transfer function:

- at every value of s where (a zero),
**increase**the slope of the line by per decade. - at every value of s where (a pole),
**decrease**the slope of the line by per decade. - The initial value of the graph depends on the boundaries. The initial point is found by putting the initial angular frequency into the function and finding .
- The initial slope of the function at the initial value depends on the number and order of zeros and poles that are at values below the initial value, and is found using the first two rules.

To handle irreducible 2nd order polynomials, can, in many cases, be approximated as .

Note that zeros and poles happen when is *equal to* a certain or . This is because the function in question is the magnitude of , and since it is a complex function, . Thus at any place where there is a zero or pole involving the term , the magnitude of that term is .

To correct a straight-line amplitude plot:

- at every zero, put a point
**above**the line, - at every pole, put a point
**below**the line, - draw a smooth curve through those points using the straight lines as asymptotes (lines which the curve approaches).

Note that this correction method does not incorporate how to handle complex values of or . In the case of an irreducible polynomial, the best way to correct the plot is to actually calculate the magnitude of the transfer function at the pole or zero corresponding to the irreducible polynomial, and put that dot over or under the line at that pole or zero.

Given a transfer function in the same form as above:

the idea is to draw separate plots for each pole and zero, then add them up. The actual phase curve is given by .

To draw the phase plot, for **each** pole and zero:

- if is positive, start line (with zero slope) at
- if is negative, start line (with zero slope) at
- if the sum of the number of unstable zeros and poles is odd, add 180° to that basis
- at every (for stable zeros ),
**increase**the slope by degrees per decade, beginning one decade before (E.g.: ) - at every (for stable poles ),
**decrease**the slope by degrees per decade, beginning one decade before (E.g.: ) - "unstable" (right half plane) poles and zeros () have opposite behavior
- flatten the slope again when the phase has changed by degrees (for a zero) or degrees (for a pole),
- After plotting one line for each pole or zero, add the lines together to obtain the final phase plot; that is, the final phase plot is the superposition of each earlier phase plot.

To create a straight-line plot for a first-order (one-pole) lowpass filter, one considers the transfer function in terms of the angular frequency:

The above equation is the normalized form of the transfer function. The Bode plot is shown in Figure 1(b) above, and construction of the straight-line approximation is discussed next.

The magnitude (in decibels) of the transfer function above, (normalized and converted to angular frequency form), given by the decibel gain expression :

then plotted versus input frequency on a logarithmic scale, can be approximated by **two lines** and it forms the asymptotic (approximate) magnitude Bode plot of the transfer function:

- the first line for angular frequencies below is a horizontal line at 0 dB since at low frequencies the term is small and can be neglected, making the decibel gain equation above equal to zero,
- the second line for angular frequencies above is a line with a slope of −20 dB per decade since at high frequencies the term dominates and the decibel gain expression above simplifies to which is a straight line with a slope of per decade.

These two lines meet at the corner frequency. From the plot, it can be seen that for frequencies well below the corner frequency, the circuit has an attenuation of 0 dB, corresponding to a unity pass band gain, i.e. the amplitude of the filter output equals the amplitude of the input. Frequencies above the corner frequency are attenuated – the higher the frequency, the higher the attenuation.

The phase Bode plot is obtained by plotting the phase angle of the transfer function given by

versus , where and are the input and cutoff angular frequencies respectively. For input frequencies much lower than corner, the ratio is small and therefore the phase angle is close to zero. As the ratio increases the absolute value of the phase increases and becomes −45 degrees when . As the ratio increases for input frequencies much greater than the corner frequency, the phase angle asymptotically approaches −90 degrees. The frequency scale for the phase plot is logarithmic.

The horizontal frequency axis, in both the magnitude and phase plots, can be replaced by the normalized (nondimensional) frequency ratio . In such a case the plot is said to be normalized and units of the frequencies are no longer used since all input frequencies are now expressed as multiples of the cutoff frequency .

Figures 2-5 further illustrate construction of Bode plots. This example with both a pole and a zero shows how to use superposition. To begin, the components are presented separately.

Figure 2 shows the Bode magnitude plot for a zero and a low-pass pole, and compares the two with the Bode straight line plots. The straight-line plots are horizontal up to the pole (zero) location and then drop (rise) at 20 dB/decade. The second Figure 3 does the same for the phase. The phase plots are horizontal up to a frequency factor of ten below the pole (zero) location and then drop (rise) at 45°/decade until the frequency is ten times higher than the pole (zero) location. The plots then are again horizontal at higher frequencies at a final, total phase change of 90°.

Figure 4 and Figure 5 show how superposition (simple addition) of a pole and zero plot is done. The Bode straight line plots again are compared with the exact plots. The zero has been moved to higher frequency than the pole to make a more interesting example. Notice in Figure 4 that the 20 dB/decade drop of the pole is arrested by the 20 dB/decade rise of the zero resulting in a horizontal magnitude plot for frequencies above the zero location. Notice in Figure 5 in the phase plot that the straight-line approximation is pretty approximate in the region where both pole and zero affect the phase. Notice also in Figure 5 that the range of frequencies where the phase changes in the straight line plot is limited to frequencies a factor of ten above and below the pole (zero) location. Where the phase of the pole and the zero both are present, the straight-line phase plot is horizontal because the 45°/decade drop of the pole is arrested by the overlapping 45°/decade rise of the zero in the limited range of frequencies where both are active contributors to the phase.

- Figure 2: Bode magnitude plot for zero and low-pass pole; curves labeled "Bode" are the straight-line Bode plots
- Figure 3: Bode phase plot for zero and low-pass pole; curves labeled "Bode" are the straight-line Bode plots
- Figure 4: Bode magnitude plot for pole-zero combination; the location of the zero is ten times higher than in Figures 2 and 3; curves labeled "Bode" are the straight-line Bode plots
- Figure 5: Bode phase plot for pole-zero combination; the location of the zero is ten times higher than in Figures 2 and 3; curves labeled "Bode" are the straight-line Bode plots

Bode plots are used to assess the stability of negative feedback amplifiers by finding the gain and phase margins of an amplifier. The notion of gain and phase margin is based upon the gain expression for a negative feedback amplifier given by

where A_{FB} is the gain of the amplifier with feedback (the **closed-loop gain**), β is the **feedback factor** and *A*_{OL} is the gain without feedback (the **open-loop gain**). The gain *A*_{OL} is a complex function of frequency, with both magnitude and phase.^{ [note 1] } Examination of this relation shows the possibility of infinite gain (interpreted as instability) if the product β*A*_{OL} = −1. (That is, the magnitude of β*A*_{OL} is unity and its phase is −180°, the so-called Barkhausen stability criterion). Bode plots are used to determine just how close an amplifier comes to satisfying this condition.

Key to this determination are two frequencies. The first, labeled here as *f*_{180}, is the frequency where the open-loop gain flips sign. The second, labeled here *f*_{0 dB}, is the frequency where the magnitude of the product | β *A*_{OL} | = 1 (in dB, magnitude 1 is 0 dB). That is, frequency *f*_{180} is determined by the condition:

where vertical bars denote the magnitude of a complex number (for example, ), and frequency *f*_{0 dB} is determined by the condition:

One measure of proximity to instability is the **gain margin**. The Bode phase plot locates the frequency where the phase of β*A*_{OL} reaches −180°, denoted here as frequency *f*_{180}. Using this frequency, the Bode magnitude plot finds the magnitude of β*A*_{OL}. If |β*A*_{OL}|_{180} = 1, the amplifier is unstable, as mentioned. If *A*_{OL}|_{180} < 1, instability does not occur, and the separation in dB of the magnitude of |β*A*_{OL}|_{180} from |β*A*_{OL}| = 1 is called the *gain margin*. Because a magnitude of one is 0 dB, the gain margin is simply one of the equivalent forms: .

Another equivalent measure of proximity to instability is the ** phase margin **. The Bode magnitude plot locates the frequency where the magnitude of |β*A*_{OL}| reaches unity, denoted here as frequency *f*_{0 dB}. Using this frequency, the Bode phase plot finds the phase of β*A*_{OL}. If the phase of β*A*_{OL}( *f*_{0 dB}) > −180°, the instability condition cannot be met at any frequency (because its magnitude is going to be < 1 when *f = f*_{180}), and the distance of the phase at *f*_{0 dB} in degrees above −180° is called the *phase margin*.

If a simple *yes* or *no* on the stability issue is all that is needed, the amplifier is stable if *f*_{0 dB} < *f*_{180}. This criterion is sufficient to predict stability only for amplifiers satisfying some restrictions on their pole and zero positions (minimum phase systems). Although these restrictions usually are met, if they are not another method must be used, such as the Nyquist plot.^{ [6] }^{ [7] } Optimal gain and phase margins may be computed using Nevanlinna–Pick interpolation theory.^{ [8] }

Figures 6 and 7 illustrate the gain behavior and terminology. For a three-pole amplifier, Figure 6 compares the Bode plot for the gain without feedback (the *open-loop* gain) *A*_{OL} with the gain with feedback *A*_{FB} (the *closed-loop* gain). See negative feedback amplifier for more detail.

In this example, *A*_{OL} = 100 dB at low frequencies, and 1 / β = 58 dB. At low frequencies, *A*_{FB} ≈ 58 dB as well.

Because the open-loop gain *A*_{OL} is plotted and not the product β *A*_{OL}, the condition *A*_{OL} = 1 / β decides *f*_{0 dB}. The feedback gain at low frequencies and for large *A*_{OL} is *A*_{FB} ≈ 1 / β (look at the formula for the feedback gain at the beginning of this section for the case of large gain *A*_{OL}), so an equivalent way to find *f*_{0 dB} is to look where the feedback gain intersects the open-loop gain. (Frequency *f*_{0 dB} is needed later to find the phase margin.)

Near this crossover of the two gains at *f*_{0 dB}, the Barkhausen criteria are almost satisfied in this example, and the feedback amplifier exhibits a massive peak in gain (it would be infinity if β *A*_{OL} = −1). Beyond the unity gain frequency *f*_{0 dB}, the open-loop gain is sufficiently small that *A*_{FB} ≈ *A*_{OL} (examine the formula at the beginning of this section for the case of small *A*_{OL}).

Figure 7 shows the corresponding phase comparison: the phase of the feedback amplifier is nearly zero out to the frequency *f*_{180} where the open-loop gain has a phase of −180°. In this vicinity, the phase of the feedback amplifier plunges abruptly downward to become almost the same as the phase of the open-loop amplifier. (Recall, *A*_{FB} ≈ *A*_{OL} for small *A*_{OL}.)

Comparing the labeled points in Figure 6 and Figure 7, it is seen that the unity gain frequency *f*_{0 dB} and the phase-flip frequency *f*_{180} are very nearly equal in this amplifier, *f*_{180} ≈ *f*_{0 dB} ≈ 3.332 kHz, which means the gain margin and phase margin are nearly zero. The amplifier is borderline stable.

Figures 8 and 9 illustrate the gain margin and phase margin for a different amount of feedback β. The feedback factor is chosen smaller than in Figure 6 or 7, moving the condition | β *A*_{OL} | = 1 to lower frequency. In this example, 1 / β = 77 dB, and at low frequencies *A*_{FB} ≈ 77 dB as well.

Figure 8 shows the gain plot. From Figure 8, the intersection of 1 / β and *A*_{OL} occurs at *f*_{0 dB} = 1 kHz. Notice that the peak in the gain *A*_{FB} near *f*_{0 dB} is almost gone.^{ [note 2] }^{ [9] }

Figure 9 is the phase plot. Using the value of *f*_{0 dB} = 1 kHz found above from the magnitude plot of Figure 8, the open-loop phase at *f*_{0 dB} is −135°, which is a phase margin of 45° above −180°.

Using Figure 9, for a phase of −180° the value of *f*_{180} = 3.332 kHz (the same result as found earlier, of course^{ [note 3] }). The open-loop gain from Figure 8 at *f*_{180} is 58 dB, and 1 / β = 77 dB, so the gain margin is 19 dB.

Stability is not the sole criterion for amplifier response, and in many applications a more stringent demand than stability is good step response. As a rule of thumb, good step response requires a phase margin of at least 45°, and often a margin of over 70° is advocated, particularly where component variation due to manufacturing tolerances is an issue.^{ [9] } See also the discussion of phase margin in the step response article.

- Figure 6: Gain of feedback amplifier
*A*_{FB}in dB and corresponding open-loop amplifier*A*_{OL}. Parameter 1/β = 58 dB, and at low frequencies*A*_{FB}≈ 58 dB as well. The gain margin in this amplifier is nearly zero because | β*A*_{OL}| = 1 occurs at almost*f*=*f*_{180°}. - Figure 7: Phase of feedback amplifier
*°A*_{FB}in degrees and corresponding open-loop amplifier*°A*_{OL}. The phase margin in this amplifier is nearly zero because the phase-flip occurs at almost the unity gain frequency*f*=*f*_{0 dB}where | β*A*_{OL}| = 1. - Figure 8: Gain of feedback amplifier
*A*_{FB}in dB and corresponding open-loop amplifier*A*_{OL}. In this example, 1 / β = 77 dB. The gain margin in this amplifier is 19 dB. - Figure 9: Phase of feedback amplifier
*A*_{FB}in degrees and corresponding open-loop amplifier*A*_{OL}. The phase margin in this amplifier is 45°.

The Bode plotter is an electronic instrument resembling an oscilloscope, which produces a Bode diagram, or a graph, of a circuit's voltage gain or phase shift plotted against frequency in a feedback control system or a filter. An example of this is shown in Figure 10. It is extremely useful for analyzing and testing filters and the stability of feedback control systems, through the measurement of corner (cutoff) frequencies and gain and phase margins.

This is identical to the function performed by a vector network analyzer, but the network analyzer is typically used at much higher frequencies.

For education/research purposes, plotting Bode diagrams for given transfer functions facilitates better understanding and getting faster results (see external links).

Two related plots that display the same data in different coordinate systems are the Nyquist plot and the Nichols plot. These are parametric plots, with frequency as the input and magnitude and phase of the frequency response as the output. The Nyquist plot displays these in polar coordinates, with magnitude mapping to radius and phase to argument (angle). The Nichols plot displays these in rectangular coordinates, on the log scale.

- A Nyquist plot.
- A Nichols plot of the same response.

This section shows that the frequency response is given by the magnitude and phase of the transfer function in Eqs.(** 1 **)-(** 2 **).

Slightly changing the requirements for Eqs.(** 1 **)-(** 2 **) one assumes that the input has been applied starting at time and one calculates the output in the limit . In this case, the output is given by the convolution

of the input signal with the inverse Laplace transform of the transfer function . Assuming that the signal becomes periodic with mean 0 and period T after a while, we can add as many periods as we want to the interval of the integral

Thus, inserting the sinusoidal input signal one obtains

Since is a real function this can be written as

The term in brackets is the definition of the Laplace transform of at . Inserting the definition in the form one obtains the output signal

- ↑ Ordinarily, as frequency increases the magnitude of the gain drops and the phase becomes more negative, although these are only trends and may be reversed in particular frequency ranges. Unusual gain behavior can render the concepts of gain and phase margin inapplicable. Then other methods such as the Nyquist plot have to be used to assess stability.
- ↑ The critical amount of feedback where the peak in the gain
*just*disappears altogether is the*maximally flat*or Butterworth design. - ↑ The frequency where the open-loop gain flips sign
*f*_{180}does not change with a change in feedback factor; it is a property of the open-loop gain. The value of the gain at*f*_{180}also does not change with a change in β. Therefore, we could use the previous values from Figures 6 and 7. However, for clarity the procedure is described using only Figures 8 and 9.

In engineering, a **transfer function** of an electronic or control system component is a mathematical function which theoretically models the device's output for each possible input. In its simplest form, this function is a two-dimensional graph of an independent scalar input versus the dependent scalar output, called a **transfer curve** or **characteristic curve**. Transfer functions for components are used to design and analyze systems assembled from components, particularly using the block diagram technique, in electronics and control theory.

A **low-pass filter** is a filter that passes signals with a frequency lower than a selected cutoff frequency and attenuates signals with frequencies higher than the cutoff frequency. The exact frequency response of the filter depends on the filter design. The filter is sometimes called a **high-cut filter**, or **treble-cut filter** in audio applications. A low-pass filter is the complement of a high-pass filter.

A **Negative-feedback amplifier** is an electronic amplifier that subtracts a fraction of its output from its input, so that negative feedback opposes the original signal. The applied negative feedback can improve its performance and reduces sensitivity to parameter variations due to manufacturing or environment. Because of these advantages, many amplifiers and control systems use negative feedback.

A **resistor–capacitor circuit**, or **RC filter** or **RC network**, is an electric circuit composed of resistors and capacitors. It may be driven by a voltage or current source and these will produce different responses. A first order RC circuit is composed of one resistor and one capacitor and is the simplest type of RC circuit.

**Chebyshev filters** are analog or digital filters having a steeper roll-off than Butterworth filters, and have passband ripple or stopband ripple. Chebyshev filters have the property that they minimize the error between the idealized and the actual filter characteristic over the range of the filter, but with ripples in the passband. This type of filter is named after Pafnuty Chebyshev because its mathematical characteristics are derived from Chebyshev polynomials. Type I Chebyshev filters are usually referred to as "Chebyshev filters", while type II filters are usually called "inverse Chebyshev filters".

**Analog signal processing** is a type of signal processing conducted on continuous analog signals by some analog means. "Analog" indicates something that is mathematically represented as a set of continuous values. This differs from "digital" which uses a series of discrete quantities to represent signal. Analog values are typically represented as a voltage, electric current, or electric charge around components in the electronic devices. An error or noise affecting such physical quantities will result in a corresponding error in the signals represented by such physical quantities.

The **step response** of a system in a given initial state consists of the time evolution of its outputs when its control inputs are Heaviside step functions. In electronic engineering and control theory, step response is the time behaviour of the outputs of a general system when its inputs change from zero to one in a very short time. The concept can be extended to the abstract mathematical notion of a dynamical system using an evolution parameter.

In control theory and signal processing, a linear, time-invariant system is said to be **minimum-phase** if the system and its inverse are causal and stable.

The **Butterworth filter** is a type of signal processing filter designed to have a frequency response as flat as possible in the passband. It is also referred to as a **maximally flat magnitude filter**. It was first described in 1930 by the British engineer and physicist Stephen Butterworth in his paper entitled "On the Theory of Filter Amplifiers".

In signal processing, a **comb filter** is a filter implemented by adding a delayed version of a signal to itself, causing constructive and destructive interference. The frequency response of a comb filter consists of a series of regularly spaced notches, giving the appearance of a comb.

**Linear phase** is a property of a filter where the phase response of the filter is a linear function of frequency. The result is that all frequency components of the input signal are shifted in time by the same constant amount, which is referred to as the group delay. Consequently, there is no phase distortion due to the time delay of frequencies relative to one another.

A **resistor–inductor circuit**, or **RL filter** or **RL network**, is an electric circuit composed of resistors and inductors driven by a voltage or current source. A first-order RL circuit is composed of one resistor and one inductor and is the simplest type of RL circuit.

In control theory and stability theory, the **Nyquist stability criterion** or **Strecker–Nyquist stability criterion**, independently discovered by the German electrical engineer Felix Strecker at Siemens in 1930 and the Swedish-American electrical engineer Harry Nyquist at Bell Telephone Laboratories in 1932, is a graphical technique for determining the stability of a dynamical system. Because it only looks at the Nyquist plot of the open loop systems, it can be applied without explicitly computing the poles and zeros of either the closed-loop or open-loop system. As a result, it can be applied to systems defined by non-rational functions, such as systems with delays. In contrast to Bode plots, it can handle transfer functions with right half-plane singularities. In addition, there is a natural generalization to more complex systems with multiple inputs and multiple outputs, such as control systems for airplanes.

The **Mason–Weaver equation** describes the sedimentation and diffusion of solutes under a uniform force, usually a gravitational field. Assuming that the gravitational field is aligned in the *z* direction, the Mason–Weaver equation may be written

A **parametric oscillator** is a driven harmonic oscillator in which the oscillations are driven by varying some parameter of the system at some frequency, typically different from the natural frequency of the oscillator. A simple example of a parametric oscillator is a child pumping a playground swing by periodically standing and squatting to increase the size of the swing's oscillations. The child's motions vary the moment of inertia of the swing as a pendulum. The "pump" motions of the child must be at twice the frequency of the swing's oscillations. Examples of parameters that may be varied are the oscillator's resonance frequency and damping .

An **all-pass filter** is a signal processing filter that passes all frequencies equally in gain, but changes the phase relationship among various frequencies. Most types of filter reduce the amplitude of the signal applied to it for some values of frequency, whereas the all-pass filter allows all frequencies through without changes in level.

**Pole splitting** is a phenomenon exploited in some forms of frequency compensation used in an electronic amplifier. When a capacitor is introduced between the input and output sides of the amplifier with the intention of moving the pole lowest in frequency to lower frequencies, pole splitting causes the pole next in frequency to move to a higher frequency. This pole movement increases the stability of the amplifier and improves its step response at the cost of decreased speed.

An **RLC circuit** is an electrical circuit consisting of a resistor (R), an inductor (L), and a capacitor (C), connected in series or in parallel. The name of the circuit is derived from the letters that are used to denote the constituent components of this circuit, where the sequence of the components may vary from RLC.

In electronics, a **transimpedance amplifier** (**TIA**) is a current to voltage converter, almost exclusively implemented with one or more operational amplifiers. The TIA can be used to amplify the current output of Geiger–Müller tubes, photo multiplier tubes, accelerometers, photo detectors and other types of sensors to a usable voltage. Current to voltage converters are used with sensors that have a current response that is more linear than the voltage response. This is the case with photodiodes where it is not uncommon for the current response to have better than 1% nonlinearity over a wide range of light input. The transimpedance amplifier presents a low impedance to the photodiode and isolates it from the output voltage of the operational amplifier. In its simplest form a transimpedance amplifier has just a large valued feedback resistor, R_{f}. The gain of the amplifer is set by this resistor and because the amplifier is in an inverting configuration, has a value of -R_{f}. There are several different configurations of transimpedance amplifiers, each suited to a particular application. The one factor they all have in common is the requirement to convert the low-level current of a sensor to a voltage. The gain, bandwidth, as well as current and voltage offsets change with different types of sensors, requiring different configurations of transimpedance amplifiers.

In thermal quantum field theory, the **Matsubara frequency** summation is the summation over discrete imaginary frequencies. It takes the following form

- ↑ R. K. Rao Yarlagadda (2010).
*Analog and Digital Signals and Systems*. Springer Science & Business Media. p. 243. ISBN 978-1-4419-0034-0. - ↑ Van Valkenburg, M. E. University of Illinois at Urbana-Champaign, "In memoriam: Hendrik W. Bode (1905-1982)", IEEE Transactions on Automatic Control, Vol. AC-29, No 3., March 1984, pp. 193-194. Quote: "Something should be said about his name. To his colleagues at Bell Laboratories and the generations of engineers that have followed, the pronunciation is boh-dee. The Bode family preferred that the original Dutch be used as boh-dah."
- ↑ "Vertaling van postbode, NL>EN". mijnwoordenboek.nl. Retrieved 2013-10-07.
- ↑ David A. Mindell
*Between Human and Machine: Feedback, Control, and Computing Before Cybernetics*JHU Press, 2004 ISBN 0801880572, pp. 127-131 - ↑ Skogestad, Sigurd; Postlewaite, Ian (2005).
*Multivariable Feedback Control*. Chichester, West Sussex, England: John Wiley & Sons, Ltd. ISBN 0-470-01167-X. - ↑ Thomas H. Lee (2004).
*The design of CMOS radio-frequency integrated circuits*(Second ed.). Cambridge UK: Cambridge University Press. p. §14.6 pp. 451–453. ISBN 0-521-83539-9. - ↑ William S Levine (1996).
*The control handbook: the electrical engineering handbook series*(Second ed.). Boca Raton FL: CRC Press/IEEE Press. p. §10.1 p. 163. ISBN 0-8493-8570-9. - ↑ Allen Tannenbaum (February 1981).
*Invariance and Systems Theory: Algebraic and Geometric Aspects*. New York, NY: Springer-Verlag. ISBN 9783540105657. - 1 2 Willy M C Sansen (2006).
*Analog design essentials*. Dordrecht, The Netherlands: Springer. pp. 157–163. ISBN 0-387-25746-2.

Wikimedia Commons has media related to Bode plots . |

- Explanation of Bode plots with movies and examples
- How to draw piecewise asymptotic Bode plots
- Summarized drawing rules (PDF)
- Bode plot applet - Accepts transfer function coefficients as input, and calculates magnitude and phase response
- Circuit analysis in electrochemistry
- Tim Green:
*Operational amplifier stability*Includes some Bode plot introduction - Gnuplot code for generating Bode plot: DIN-A4 printing template (pdf)
- MATLAB function for creating a Bode plot of a system
- MATLAB Tech Talk videos explaining Bode plots and showing how to use them for control design
- Insert the poles and zeros and this website will draw the asymptotic and accurate Bode plots
- Mathematica function for creating the Bode plot

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